View LT1936_268359.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

LT1936 1.4A, 500kHz Step-Down Switching Regulator
FEATURES

DESCRIPTIO
Wide Input Range: 3.6V to 36V Short-Circuit Protected Over Full Input Range 1.9A Guaranteed Minimum Switch Current 5V at 1.4A from 10V to 36V Input 3.3V at 1.4A from 7V to 36V Input 5V at 1.2A from 6.3V to 36V Input 3.3V at 1.2A from 4.5V to 36V Input Output Adjustable Down to 1.20V 500kHz Fixed Frequency Operation Soft-Start Uses Small Ceramic Capacitors Internal or External Compensation Low Shutdown Current: <2A Thermally Enhanced 8-Lead MSOP Package
The LT(R)1936 is a current mode PWM step-down DC/DC converter with an internal 1.9A power switch, packaged in a tiny, thermally enhanced 8-lead MSOP. The wide input range of 3.6V to 36V makes the LT1936 suitable for regulating power from a wide variety of sources, including automotive batteries, 24V industrial supplies and unregulated wall adapters. Its high operating frequency allows the use of small, low cost inductors and ceramic capacitors, resulting in low, predictable output ripple. Cycle-by-cycle current limit, frequency foldback and thermal shutdown provide protection against shorted outputs, and soft-start eliminates input current surge during startup. Transient response can be optimized by using external compensation components, or board space can be minimized by using internal compensation. The low current (<2A) shutdown mode enables easy power management in battery-powered systems.
, LTC and LT are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners.
APPLICATIO S

Automotive Battery Regulation Industrial Control Supplies Unregulated Wall Adapters
TYPICAL APPLICATIO
VIN 4.5V TO 36V VIN ON OFF 4.7F SHDN LT1936
3.3V Step-Down Converter
95
0.22F 10H
VIN = 12V VOUT = 5V
BOOST SW
90 85
EFFICIENCY (%)
17.4k COMP VC FB GND 10k
VOUT 3.3V 1.2A
80 75 70
22F
1936 TA01a
65
0
U
Efficiency
VOUT = 3.3V 0.5 1 LOAD CURRENT (A) 1.5
1936 TA01b
U
U
1936f
1
LT1936
ABSOLUTE
(Note 1)
AXI U
RATI GS
PACKAGE/ORDER I FOR ATIO
ORDER PART NUMBER
TOP VIEW BOOST VIN SW GND 1 2 3 4 8 7 6 5 COMP VC FB SHDN 9
VIN Voltage ............................................... - 0.4V to 36V BOOST Voltage ........................................................ 43V BOOST Above SW Voltage ....................................... 20V SHDN Voltage ........................................... - 0.4V to 36V FB, VC, COMP Voltage ............................................... 6V Operating Temperature Range (Note 2) LT1936E ............................................. - 40C to 85C LT1936I ............................................ - 40C to 125C Maximum Junction Temperature .......................... 125C Storage Temperature Range ................. - 65C to 150C Lead Temperature (Soldering, 10 sec).................. 300C
LT1936EMS8E LT1936IMS8E MS8E PART MARKING LTBMT LTBRV
MS8E PACKAGE 8-LEAD PLASTIC MSOP TJMAX = 125C, JA = 40C/W EXPOSED PAD (PIN 9) IS GND MUST BE CONNECTED TO PCB
Consult factory for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS
The denotes specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. VIN = 12V, VBOOST = 17V, unless otherwise noted. (Note 2)
PARAMETER Undervoltage Lockout Quiescent Current Quiescent Current in Shutdown FB Voltage FB Pin Bias Current FB Voltage Line Regulation Error Amp gm Error Amp Voltage Gain VC Clamp VC Switch Threshold Internal Compensation R Internal Compensation C COMP Pin Leakage Switching Frequency Maximum Duty Cycle Switch Current Limit Switch VCESAT Switch Leakage Current Minimum BOOST Voltage Above SW BOOST Pin Current BOOST Pin Leakage ISW = 1.2A ISW = 1.2A VSW = 0V 2 28 0.1 ISW = 1.2A VCOMP = 1V VCOMP = 1.8V VFB = 1.1V VFB = 0V

CONDITIONS VFB = 1.5V VSHDN = 0V
MIN
TYP 3.45 1.8 0.1
MAX 3.6 2.5 2 1.215 200
UNITS V mA A V nA %/V S V V k pF
1.175
1.200 50 0.01 250 150 1.8 0.7 50 150
VFB = 1.20V (Note 4) VIN = 5V to 36V VC = 0.5V, IVC = 5A VC = 0.8V, 1.2V
1 400 87 1.9 500 40 92 2.2 410 2.6 520 2 2.2 50 1 600
2
U
A kHz kHz % A mV A V mA A
1936f
W
U
U
WW
W
LT1936
ELECTRICAL CHARACTERISTICS
The denotes specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. VIN = 12V, VBOOST = 17V, unless otherwise noted. (Note 2)
PARAMETER SHDN Input Voltage High SHDN Input Voltage Low SHDN Pin Current VSHDN = 2.3V (Note 5) VSHDN = 12V VSHDN = 0V 34 140 0.01 CONDITIONS MIN 2.3 0.3 50 240 0.1 TYP MAX UNITS V V A A A
Note 1: Absolute Maximum Ratings are those values beyond which the life of the device may be impaired. Note 2: The LT1936E is guaranteed to meet performance specifications from 0C to 70C. Specifications over the -40C to 85C operating temperature range are assured by design, characterization and correlation with statistical process controls. The LT1936I specifications are guaranteed over the -40C to 125C temperature range.
Note 3: Current limit guaranteed by design and/or correlation to static test. Slope compensation reduces current limit at higher duty cycle. Note 4: Current flows out of pin. Note 5: Current flows into pin.
TYPICAL PERFOR A CE CHARACTERISTICS
Efficiency, VOUT = 5V
100 100
CURRENT LIMIT (A)
90
VIN = 12V VIN = 24V
EFFICIENCY (%)
EFFICIENCY (%)
80
70
VOUT = 5V TA = 25C D1 = DFLS140L L1 = 15H, TOKO D63CB 0 0.5 1.0 LOAD CURRENT (A) 1.5
1936 G01
60
UW
Efficiency, VOUT = 3.3V
3.0 2.5 90 VIN = 5V 2.0 1.5 1.0 0.5 0 0 0.5 1.0 LOAD CURRENT (A) 1.5
1936 G02
Switch Current Limit
TYP MIN
VIN = 12V 80 VIN = 24V
70
VOUT = 3.3V TA = 25C D1 = DFLS140L L1 = 10H, TOKO D63CB
60
0
20
40 60 DUTY CYCLE (%)
80
100
1936 G03
1936f
3
LT1936 TYPICAL PERFOR A CE CHARACTERISTICS
Maximum Load Current
1.8 VOUT = 5V 1.8
SWITCH VOLTAGE DROP (mV)
1.6
LOAD CURRENT (A)
LOAD CURRENT (A)
L = 15H 1.4 L = 10H
1.2
1.0 0 5 10 15 20 INPUT VOLTAGE (V) 25 30
1936 G04
Feedback Voltage
1.210
3.8
1.205
FEEDBACK VOLTAGE (V)
3.6
UVLO (V)
SWITCHING FREQUENCY (kHz)
1.200
1.195
1.190
1.185 -50 -25
50 25 0 75 TEMPERATURE (C)
Frequency Foldback
700 600
SWITCH CURRENT LIMIT (A)
TA = 25C
SWITCHING FREQUENCY (kHz)
SHDN PIN CURRENT (A)
500 400 300 200 100 0 0 1.0 0.5 FB PIN VOLTAGE (V) 1.5
1936 G10
4
UW
100
1936 G07
Maximum Load Current
600 VOUT = 3.3V 500 400 300 200 100 0 0 5 10 15 20 INPUT VOLTAGE (V) 25 30
1936 G05
Switch Voltage Drop
1.6 L = 10H
TA = 85C TA = 25C TA = -45C
1.4 L = 6.8H 1.2
1.0
0
0.5 1.0 SWITCH CURRENT (A)
1.5
1936 G06
Undervoltage Lockout
600
Switching Frequency
550
3.4
500
3.2
450
125
3.0 -50
-25
75 0 25 50 TEMPERATURE (C)
100
125
400 -50
-25
75 0 25 50 TEMPERATURE (C)
100
125
1936 G08
1936 G09
Soft-Start
3.0 2.5
150
SHDN Pin Current
200 TA = 25C
TA = 25C DC = 30%
2.0 1.5 1.0 0.5 0 0 1 2 3 SHDN PIN VOLTAGE (V) 4
1936 G11
100
50
0 0 12 4 8 SHDN PIN VOLTAGE (V) 16
1936 G12
1936f
LT1936 TYPICAL PERFOR A CE CHARACTERISTICS
Minimum Input Voltage
8 VOUT = 5V TA = 25C L = 15H TO START
INPUT VOLTAGE (V)
7
INPUT VOLTAGE (V)
TO START 5.0 4.5 4.0 3.5 TO RUN
SWITCH CURRENT LIMIT (A)
6 TO RUN 5
4
1
100 10 LOAD CURRENT (mA)
Switching Waveforms
VSW 10V/DIV IL 500mA/DIV VOUT 20mV/DIV VIN = 12V VOUT = 3.3V IOUT = 1A L = 10H COUT = 22F 1s/DIV
1936 G16
VC Voltages
2.5
2.0
VC VOLTAGE (V)
CURRENT LIMIT CLAMP 1.5
VC PIN CURRENT (A)
1.0 SWITCHING THRESHOLD 0.5
0 -50
-25
50 25 0 75 TEMPERATURE (C)
UW
1000
1936 G13
Minimum Input Voltage
6.0 5.5 VOUT = 3.3V TA = 25C L = 10H
3.0 2.5 2.0 1.5 1.0 0.5
Switch Current Limit
3.0 0 10 100 LOAD CURRENT (mA) 1000
1936 G14
0 -50 -25
50 25 75 0 TEMPERATURE (C)
100
125
1936 G15
Switching Waveforms, Discontinuous Mode
VSW 10V/DIV IL 500mA/DIV VOUT 20mV/DIV VIN = 12V VOUT = 3.3V IOUT = 50mA L = 10H COUT = 22F 1s/DIV
1936 G17
Error Amp Output Current
60 40 20 0 -20 -40 -60
100 125
TA = 25C VC = 0.5V
0
1 FB PIN VOLTAGE (V)
2
1936 G19
1936 G18
1936f
5
LT1936
PI FU CTIO S
BOOST (Pin 1): The BOOST pin is used to provide a drive voltage, higher than the input voltage, to the internal bipolar NPN power switch. VIN (Pin 2): The VIN pin supplies current to the LT1936's internal regulator and to the internal power switch. This pin must be locally bypassed. SW (Pin 3): The SW pin is the output of the internal power switch. Connect this pin to the inductor, catch diode and boost capacitor. GND (Pin 4): Tie the GND pin to a local ground plane below the LT1936 and the circuit components. Return the feedback divider to this pin. SHDN (Pin 5): The SHDN pin is used to put the LT1936 in shutdown mode. Tie to ground to shut down the LT1936. Tie to 2.3V or more for normal operation. If the shutdown feature is not used, tie this pin to the VIN pin. SHDN also provides a soft-start function; see the Applications Information. Do not drive SHDN more than 5V above VIN. FB (Pin 6): The LT1936 regulates its feedback pin to 1.200V. Connect the feedback resistor divider tap to this pin. Set the output voltage according to VOUT = 1.200V (1 + R1/R2). A good value for R2 is 10k. VC (Pin 7): The VC pin is used to compensate the LT1936 control loop by tying an external RC network from this pin to ground. The COMP pin provides access to an internal RC network that can be used instead of the external components. COMP (Pin 8): To use the internal compensation network, tie the COMP pin to the VC pin. Otherwise, tie COMP to ground or leave it floating. Exposed Pad (Pin 9): The Exposed Pad must be soldered to the PCB and electrically connected to ground. Use a large ground plane and thermal vias to optimize thermal performance.
BLOCK DIAGRA
VIN C2 2 VIN
ON OFF R3 5 C4 SHDN
6
W
U
U
U
INT REG AND UVLO
SLOPE COMP
R S Q
BOOST
D2 1
C3 Q DRIVER Q1 SW L1 3 D1 C1 VOUT
OSC FREQUENCY FOLDBACK
R1 FB VC gm CC 150pF 6 R2
RC 50k VC R4 C5 COMP
1.200V
7
8
4
GND
1936 BD
1936f
LT1936
OPERATIO
The LT1936 is a constant frequency, current mode stepdown regulator. A 500kHz oscillator enables an RS flipflop, turning on the internal 1.9A power switch Q1. An amplifier and comparator monitor the current flowing between the VIN and SW pins, turning the switch off when this current reaches a level determined by the voltage at VC. An error amplifier measures the output voltage through an external resistor divider tied to the FB pin and servos the VC pin. If the error amplifier's output increases, more current is delivered to the output; if it decreases, less current is delivered. An active clamp (not shown) on the VC pin provides current limit. The VC pin is also clamped to the voltage on the SHDN pin; soft-start is implemented by generating a voltage ramp at the SHDN pin using an external resistor and capacitor.
U
(Refer to Block Diagram)
An internal regulator provides power to the control circuitry. This regulator includes an undervoltage lockout to prevent switching when VIN is less than ~3.45V. The SHDN pin is used to place the LT1936 in shutdown, disconnecting the output and reducing the input current to less than 2A. The switch driver operates from either the input or from the BOOST pin. An external capacitor and diode are used to generate a voltage at the BOOST pin that is higher than the input supply. This allows the driver to fully saturate the internal bipolar NPN power switch for efficient operation. The oscillator reduces the LT1936's operating frequency when the voltage at the FB pin is low. This frequency foldback helps to control the output current during startup and overload.
1936f
7
LT1936
APPLICATIO S I FOR ATIO
FB Resistor Network
The output voltage is programmed with a resistor divider between the output and the FB pin. Choose the 1% resistors according to: V R1 = R2 OUT - 1 1.200 R2 should be 20k or less to avoid bias current errors. Reference designators refer to the Block Diagram. Input Voltage Range The input voltage range for LT1936 applications depends on the output voltage and the Absolute Maximum Ratings of the VIN and BOOST pins. The minimum input voltage is determined by either the LT1936's minimum operating voltage of ~3.45V or by its maximum duty cycle. The duty cycle is the fraction of time that the internal switch is on and is determined by the input and output voltages:
VOUT + VD DC = VIN - VSW + VD
where VD is the forward voltage drop of the catch diode (~0.5V) and VSW is the voltage drop of the internal switch (~0.5V at maximum load). This leads to a minimum input voltage of:
VIN(MIN) =
VOUT + VD - VD + VSW DCMAX
with DCMAX = 0.87. The maximum input voltage is determined by the absolute maximum ratings of the VIN and BOOST pins and by the minimum duty cycle DCMIN = 0.08:
VIN(MAX) =
VOUT + VD - VD + VSW DCMIN
Note that this is a restriction on the operating input voltage; the circuit will tolerate transient inputs up to the absolute maximum ratings of the VIN and BOOST pins.
8
U
Inductor Selection and Maximum Output Current A good first choice for the inductor value is L = 2.2 (VOUT + VD) where VD is the voltage drop of the catch diode (~0.4V) and L is in H. With this value the maximum output current will be above 1.2A at all duty cycles and greater than 1.4A for duty cycles less than 50% (VIN > 2 VOUT). The inductor's RMS current rating must be greater than the maximum load current and its saturation current should be about 30% higher. For robust operation in fault conditions (start-up or short circuit) and high input voltage (>30V), the saturation current should be above 2.6A. To keep the efficiency high, the series resistance (DCR) should be less than 0.1, and the core material should be intended for high frequency applications. Table 1 lists several vendors and suitable types.
Table 1. Inductor Vendors
VENDOR Murata TDK Toko URL www.murata.com www.component.tdk.com www.toko.com PART SERIES LQH55D SLF7045 SLF10145 D62CB D63CB D75C D75F CR54 CDRH74 CDRH6D38 CR75 TYPE Open Shielded Shielded Shielded Shielded Shielded Open Open Shielded Shielded Open Sumida www.sumida.com
W
U
U
Of course, such a simple design guide will not always result in the optimum inductor for your application. A larger value provides a slightly higher maximum load current and will reduce the output voltage ripple. If your load is lower than 1.2A, then you can decrease the value of the inductor and operate with higher ripple current. This allows you to use a physically smaller inductor, or one with a lower DCR resulting in higher efficiency. Be aware that if the inductance differs from the simple rule above, then the maximum load current will depend on input voltage. There are several graphs in the Typical Performance Characteristics section
1936f
LT1936
APPLICATIO S I FOR ATIO
of this data sheet that show the maximum load current as a function of input voltage and inductor value for several popular output voltages. Low inductance may result in discontinuous mode operation, which is okay but further reduces maximum load current. For details of maximum output current and discontinuous mode operation, see Linear Technology Application Note 44. Finally, for duty cycles greater than 50% (VOUT/VIN < 0.5), there is a minimum inductance required to avoid subharmonic oscillations. Choosing L greater than 1.6 (VOUT + VD) H prevents subharmonic oscillations at all duty cycles. Catch Diode A 1A Schottky diode is recommended for the catch diode, D1. The diode must have a reverse voltage rating equal to or greater than the maximum input voltage. The ON Semiconductor MBRM140 is a good choice. It is rated for 1A DC at a case temperature of 110C and 1.5A at a case temperature of 95C. Diode Incorporated's DFLS140L is rated for 1.1A average current; the DFLS240L is rated for 2A average current. The average diode current in an LT1936 application is approximately IOUT (1 - DC). Input Capacitor Bypass the input of the LT1936 circuit with a 4.7F or higher value ceramic capacitor of X7R or X5R type. Y5V types have poor performance over temperature and applied voltage, and should not be used. A 4.7F ceramic is adequate to bypass the LT1936 and will easily handle the ripple current. However, if the input power source has high impedance, or there is significant inductance due to long wires or cables, additional bulk capacitance may be necessary. This can be provided with a low performance electrolytic capacitor. Step-down regulators draw current from the input supply in pulses with very fast rise and fall times. The input capacitor is required to reduce the resulting voltage ripple at the LT1936 and to force this very high frequency switching current into a tight local loop, minimizing EMI. A 4.7F capacitor is capable of this task, but only if it is placed close to the LT1936 and the catch diode; see the PCB Layout section. A second precaution regarding the ceramic input capacitor concerns the maximum input
U
voltage rating of the LT1936. A ceramic input capacitor combined with trace or cable inductance forms a high quality (under damped) tank circuit. If the LT1936 circuit is plugged into a live supply, the input voltage can ring to twice its nominal value, possibly exceeding the LT1936's voltage rating. This situation is easily avoided; see the Hot Plugging Safety section. For space sensitive applications, a 2.2F ceramic capacitor can be used for local bypassing of the LT1936 input. However, the lower input capacitance will result in increased input current ripple and input voltage ripple, and may couple noise into other circuitry. Also, the increased voltage ripple will raise the minimum operating voltage of the LT1936 to ~3.7V. Output Capacitor The output capacitor has two essential functions. Along with the inductor, it filters the square wave generated by the LT1936 to produce the DC output. In this role it determines the output ripple, and low impedance at the switching frequency is important. The second function is to store energy in order to satisfy transient loads and stabilize the LT1936's control loop. Ceramic capacitors have very low equivalent series resistance (ESR) and provide the best ripple performance. A good value is:
W
U
U
COUT =
150 VOUT
where COUT is in F. Use X5R or X7R types. This choice will provide low output ripple and good transient response. Transient performance can be improved with a high value capacitor if the compensation network is also adjusted to maintain the loop bandwidth. A lower value of output capacitor can be used, but transient performance will suffer. With an external compensation network, the loop gain can be lowered to compensate for the lower capacitor value. When using the internal compensation network, the lowest value for stable operation is:
COUT > 66 VOUT
1936f
9
LT1936
APPLICATIO S I FOR ATIO
Table 2. Capacitor Vendors
Vendor Panasonic Phone (714) 373-7366
URL www.panasonic.com
Kemet Sanyo
(864) 963-6300 (408) 749-9714
www.kemet.com www.sanyovideo.com
Murata AVX Taiyo Yuden
(404) 436-1300
www.murata.com www.avxcorp.com
(864) 963-6300
www.taiyo-yuden.com
This is the minimum output capacitance required, not the nominal capacitor value. For example, a 3.3V output requires 20F of output capacitance. If a small 22F, 6.3V ceramic capacitor is used, the circuit may be unstable because the effective capacitance is lower than the nominal capacitance when biased at 3.3V. Look carefully at the capacitor's data sheet to find out what the actual capacitance is under operating conditions (applied voltage and temperature). A physically larger capacitor, or one with a higher voltage rating, may be required. High performance electrolytic capacitors can be used for the output capacitor. Low ESR is important, so choose one that is intended for use in switching regulators. The ESR should be specified by the supplier, and should be 0.05 or less. Such a capacitor will be larger than a ceramic capacitor and will have a larger capacitance, because the capacitor must be large to achieve low ESR. Table 2 lists several capacitor vendors. Frequency Compensation The LT1936 uses current mode control to regulate the output. This simplifies loop compensation. In particular, the LT1936 does not require the ESR of the output capacitor for stability, so you are free to use ceramic capacitors to achieve low output ripple and small circuit size. Frequency compensation is provided by the components tied to the VC pin, as shown in Figure 1. Generally a capacitor (CC) and a resistor (RC) in series to ground are used. In addition, there may be lower value capacitor in
gm = 250mho 600k
50k VC CF RC CC
150pF GND POLYMER OR TANTALUM R2 CERAMIC
COMP
Figure 1. Model for Loop Response
1936f
10
-
+
U
Part Series Ceramic, Polymer, Tantalum Ceramic, Tantalum Ceramic, Polymer, Tantalum Ceramic Ceramic, Tantalum Ceramic TPS Series Comments EEF Series T494, T495 POSCAP
W
U
U
parallel. This capacitor (CF) is not part of the loop compensation but is used to filter noise at the switching frequency, and is required only if a phase-lead capacitor is used or if the output capacitor has high ESR. An alternative to using external compensation components is to use the internal RC network by tying the COMP pin to the VC pin. This reduces component count but does not provide the optimum transient response when the output capacitor value is high, and the circuit may not be stable when the output capacitor value is low. If the internal compensation network is not used, tie COMP to ground or leave it floating. Loop compensation determines the stability and transient performance. Designing the compensation network is a
LT1936 CURRENT MODE POWER STAGE gm = 2mho SW ERROR AMPLIFIER FB ESR R1 CPL OUTPUT
1.25V
+
C1
C1
1936 F01
LT1936
APPLICATIO S I FOR ATIO
bit complicated and the best values depend on the application and in particular the type of output capacitor. A practical approach is to start with one of the circuits in this data sheet that is similar to your application and tune the compensation network to optimize the performance. Stability should then be checked across all operating conditions, including load current, input voltage and temperature. The LT1375 data sheet contains a more thorough discussion of loop compensation and describes how to test the stability using a transient load. Figure 1 shows an equivalent circuit for the LT1936 control loop. The error amplifier is a transconductance amplifier with finite output impedance. The power section, consisting of the modulator, power switch and inductor, is modeled as a transconductance amplifier generating an
COUT = 22F (AVX 1210ZD226MAT) (2a)
COMP VC VOUT 100mV/DIV
COUT = 22F x2 (2b)
COMP VC VOUT 100mV/DIV
COUT = 150F (4TPC150M) (2c)
COMP VC VOUT 100mV/DIV
COUT = 150F (4TPC150M) (2d)
COMP VC 220k 100pF
IOUT 500mA/DIV
Figure 2. Transient Load Response of the LT1936 with Different Output Capacitors as the Load Current is Stepped from 200mA to 800mA. VOUT = 3.3V
1936f
U
output current proportional to the voltage at the VC pin. Note that the output capacitor integrates this current, and that the capacitor on the VC pin (CC) integrates the error amplifier output current, resulting in two poles in the loop. In most cases a zero is required and comes from either the output capacitor ESR or from a resistor RC in series with CC. This simple model works well as long as the value of the inductor is not too high and the loop crossover frequency is much lower than the switching frequency. A phase lead capacitor (CPL) across the feedback divider may improve the transient response. Figure 2 compares the transient response across several output capacitor choices and compensation schemes. In each case the load current is stepped from 200mA to 800mA and back to 200mA.
VOUT 100mV/DIV 800mA 200mA
1936 F02
W
U
U
50s/DIV
11
LT1936
APPLICATIO S I FOR ATIO
BOOST Pin Considerations
Capacitor C3 and diode D2 are used to generate a boost voltage that is higher than the input voltage. In most cases a 0.22F capacitor and fast switching diode (such as the 1N4148 or 1N914) will work well. Figure 3 shows two ways to arrange the boost circuit. The BOOST pin must be at least 2.3V above the SW pin for best efficiency. For outputs of 3V and above, the standard circuit (Figure 3a) is best. For outputs between 2.8V and 3V, use a 0.47F capacitor and a Schottky diode. For lower output voltages the boost diode can be tied to the input (Figure 3b), or to another supply greater than 2.8V. The circuit in Figure 3a is more efficient because the BOOST pin current comes from a lower voltage. You must also be sure that the maximum voltage rating of the BOOST pin is not exceeded. A 2.5V output presents a special case. This is a popular output voltage, and the advantage of connecting the boost circuit to the output is that the circuit will accept a 36V maximum input voltage rather than 20V (due to the BOOST pin rating). However, 2.5V is marginally adequate to support the boosted drive stage at low ambient temperatures. Therefore, special care and some restrictions on operation are necessary when powering the BOOST pin from a 2.5V output. Minimize the voltage loss in the boost circuit by using a 1F boost capacitor and a good, low drop
D2
BOOST LT1936 VIN VIN GND VBOOST - VSW VOUT MAX VBOOST VIN + VOUT D2 (3a) SW
C3 VOUT
BOOST LT1936 VIN VIN GND SW
C3 VOUT
1933 F03
VBOOST - VSW VIN MAX VBOOST 2VIN (3b)
Figure 3. Two Circuits for Generating the Boost Voltage
12
U
Schottky diode (such as the ON Semi MBR0540). Because the required boost voltage increases at low temperatures, the circuit will supply only 1A of output current when the ambient temperature is -45C, increasing to 1.2A at 0C. Also, the minimum input voltage to start the boost circuit is higher at low temperature. See the Typical Applications section for a 2.5V schematic and performance curves. The minimum operating voltage of an LT1936 application is limited by the undervoltage lockout (~3.45V) and by the maximum duty cycle as outlined above. For proper startup, the minimum input voltage is also limited by the boost circuit. If the input voltage is ramped slowly, or the LT1936 is turned on with its SHDN pin when the output is already in regulation, then the boost capacitor may not be fully charged. Because the boost capacitor is charged with the energy stored in the inductor, the circuit will rely on some minimum load current to get the boost circuit running properly. This minimum load will depend on input and output voltages, and on the arrangement of the boost circuit. The minimum load generally goes to zero once the circuit has started. Figure 4 shows a plot of minimum load to start and to run as a function of input voltage. In many cases the discharged output capacitor will present a load to the switcher, which will allow it to start. The plots show the worst-case situation where VIN is ramping very slowly. For lower start-up voltage, the boost diode can be tied to VIN; however, this restricts the input range to one-half of the absolute maximum rating of the BOOST pin. At light loads, the inductor current becomes discontinuous and the effective duty cycle can be very high. This reduces the minimum input voltage to approximately 300mV above VOUT. At higher load currents, the inductor current is continuous and the duty cycle is limited by the maximum duty cycle of the LT1936, requiring a higher input voltage to maintain regulation. Soft-Start The SHDN pin can be used to soft-start the LT1936, reducing the maximum input current during start-up. The SHDN pin is driven through an external RC filter to create a voltage ramp at this pin. Figure 5 shows the start-up waveforms with and without the soft-start circuit. By choosing a large RC time constant, the peak start-up
1936f
W
U
U
LT1936
APPLICATIO S I FOR ATIO
Minimum Input Voltage VOUT = 3.3V
6.0 5.5 INPUT VOLTAGE (V) 5.0 4.5 4.0 3.5 3.0 0 10 100 LOAD CURRENT (mA) 1000
1936 G14
VOUT = 3.3V TA = 25C L = 10H
INPUT VOLTAGE (V)
TO START
TO RUN
Figure 4. The Minimum Input Voltage Depends on Output Voltage, Load Current and Boost Circuit
RUN
SHDN GND
RUN 15k SHDN 0.22F GND
Figure 5. To Soft-Start the LT1936, Add a Resistor and Capacitor to the SHDN Pin. VIN = 12V, VOUT = 3.3V, COUT = 2 x 22F, RLOAD = 3.3
current can be reduced to the current that is required to regulate the output, with no overshoot. Choose the value of the resistor so that it can supply 60A when the SHDN pin reaches 2.3V. Shorted and Reversed Input Protection If the inductor is chosen so that it won't saturate excessively, an LT1936 buck regulator will tolerate a shorted output. There is another situation to consider in systems
U
Minimum Input Voltage VOUT = 5V
8 VOUT = 5V TA = 25C L = 15H TO START 7 6 TO RUN 5 4 1 100 10 LOAD CURRENT (mA) 1000
1936 G13
W
U
U
RUN 5V/DIV IIN 500mA/DIV
VOUT 5V/DIV 50s/DIV
1936 F05a
RUN 5V/DIV IIN 500mA/DIV
VOUT 5V/DIV 0.5ms/DIV
1936 F05b
where the output will be held high when the input to the LT1936 is absent. This may occur in battery charging applications or in battery backup systems where a battery or some other supply is diode OR-ed with the LT1936's output. If the VIN pin is allowed to float and the SHDN pin is held high (either by a logic signal or because it is tied to VIN), then the LT1936's internal circuitry will pull its quiescent current through its SW pin. This is fine if your system can tolerate a few mA in this state. If you ground
1936f
13
LT1936
APPLICATIO S I FOR ATIO
the SHDN pin, the SW pin current will drop to essentially zero. However, if the VIN pin is grounded while the output is held high, then parasitic diodes inside the LT1936 can pull large currents from the output through the SW pin and the VIN pin. Figure 6 shows a circuit that will run only when the input voltage is present and that protects against a shorted or reversed input.
D4 MBRS140 VIN VIN SHDN VC COMP GND FB BACKUP BOOST LT1936 SW VOUT
1936 F06
Figure 6. Diode D4 Prevents a Shorted Input from Discharging a Backup Battery Tied to the Output; It Also Protects the Circuit from a Reversed Input. The LT1936 Runs Only When the Input is Present
PCB Layout For proper operation and minimum EMI, care must be taken during printed circuit board layout. Figure 7 shows the recommended component placement with trace, ground plane and via locations. Note that large, switched currents flow in the LT1936's VIN and SW pins, the catch diode (D1) and the input capacitor (C2). The loop formed by these components should be as small as possible. These components, along with the inductor and output capacitor, should be placed on the same side of the circuit board, and their connections should be made on that layer. Place a local, unbroken ground plane below these components. The SW and BOOST nodes should be as small as possible. Finally, keep the FB and VC nodes small so that the ground traces will shield them from the SW and BOOST nodes. The Exposed Pad on the bottom of the package must be soldered to ground so that the pad acts as a heat sink. To keep thermal resistance low, extend the ground plane as much as possible, and add thermal vias under and near the LT1936 to additional ground planes within the circuit board and on the bottom side.
14
U
IN MINIMIZE LT1936 C2, D1 LOOP D2 C2 R4 GND C3 R2 R1 L1 C1 D1 GND OUT VIAS
1936 F07
W
U
U
Figure 7. A Good PCB Layout Ensures Low EMI Operation
High Temperature Considerations The die temperature of the LT1936 must be lower than the maximum rating of 125C. This is generally not a concern unless the ambient temperature is above 85C. For higher temperatures, care should be taken in the layout of the circuit to ensure good heat sinking of the LT1936. The maximum load current should be derated as the ambient temperature approaches 125C. The die temperature is calculated by multiplying the LT1936 power dissipation by the thermal resistance from junction to ambient. Power dissipation within the LT1936 can be estimated by calculating the total power loss from an efficiency measurement and subtracting the catch diode loss. The resulting temperature rise at full load is nearly independent of input voltage. Thermal resistance depends on the layout of the circuit board, but values from 40C/W to 60C/W are typical. Die temperature rise was measured on a 4-layer, 5cm x 6.5cm circuit board in still air at a load current of 1.4A. For 12V input to 3.3V output the die temperature elevation above ambient was 26C; for 24V in to 3.3V out the rise was 31C; for 12V in to 5V the rise was 31C and for 24V in to 5V the rise was 34C.
1936f
LT1936
APPLICATIO S I FOR ATIO
Hot Plugging Safely
The small size, robustness and low impedance of ceramic capacitors make them an attractive option for the input bypass capacitor of LT1936 circuits. However, these capacitors can cause problems if the LT1936 is plugged into a live supply (see Linear Technology Application Note 88 for a complete discussion). The low loss ceramic capacitor combined with stray inductance in series with the power source forms an under damped tank circuit, and the voltage at the VIN pin of the LT1936 can ring to twice the
CLOSING SWITCH SIMULATES HOT PLUG IIN VIN LT1936
+
4.7F
LOW IMPEDANCE ENERGIZED 24V SUPPLY
STRAY INDUCTANCE DUE TO 6 FEET (2 METERS) OF TWISTED PAIR
+
22F 35V AI.EI.
+
4.7F IIN 10A/DIV
0.7 LT1936
+
0.1F 4.7F IIN 10A/DIV
Figure 8. A Well Chosen Input Network Prevents Input Voltage Overshoot and Ensures Reliable Operation When the LT1936 is Connected to a Live Supply
1936f
U
nominal input voltage, possibly exceeding the LT1936's rating and damaging the part. If the input supply is poorly controlled or the user will be plugging the LT1936 into an energized supply, the input network should be designed to prevent this overshoot. Figure 8 shows the waveforms that result when an LT1936 circuit is connected to a 24V supply through six feet of 24-gauge twisted pair. The first plot is the response with a 4.7F ceramic capacitor at the input. The input voltage rings as high as 50V and the input current peaks at 26A. One
DANGER VIN 20V/DIV RINGING VIN MAY EXCEED ABSOLUTE MAXIMUM RATING OF THE LT1936 IIN 10A/DIV 20s/DIV
W
U
U
(8a)
LT1936
VIN 20V/DIV
(8b)
20s/DIV
VIN 20V/DIV
(8c)
20s/DIV
1936 F08
15
LT1936
APPLICATIO S I FOR ATIO
method of damping the tank circuit is to add another capacitor with a series resistor to the circuit. In Figure 8b an aluminum electrolytic capacitor has been added. This capacitor's high equivalent series resistance damps the circuit and eliminates the voltage overshoot. The extra capacitor improves low frequency ripple filtering and can slightly improve the efficiency of the circuit, though it is likely to be the largest component in the circuit. An alternative solution is shown in Figure 8c. A 0.7 resistor is added in series with the input to eliminate the voltage overshoot (it also reduces the peak input current). A 0.1F capacitor improves high frequency filtering. This solution is smaller and less expensive than the electrolytic capacitor. For high
TYPICAL APPLICATIO S
3.3V Step-Down Converter
D2 VIN 4.5V TO 36V VIN ON OFF C1 4.7F SHDN LT1936 COMP VC FB GND R2 10k C2 47F BOOST SW D1 R1 17.4k VOUT 3.3V 1.2A C3 0.22F
VIN 6.3V TO 36V VIN ON OFF C1 4.7F SHDN LT1936 COMP VC FB GND BOOST SW
16
U
input voltages its impact on efficiency is minor, reducing efficiency by one percent for a 5V output at full load operating from 24V. Other Linear Technology Publications Application Notes 19, 35 and 44 contain more detailed descriptions and design information for buck regulators and other switching regulators. The LT1376 data sheet has a more extensive discussion of output ripple, loop compensation and stability testing. Design Note 100 shows how to generate a bipolar output supply using a buck regulator.
L1 10H
1936 TA03
W
U
U
U
5V Step-Down Converter
D2 C3 0.22F
L1 15H R1 31.6k VOUT 5V 1.2A C2 22F
D1
R2 10k
1936 TA04
1936f
LT1936
TYPICAL APPLICATIO S
1.8V Step-Down Converter
D2 VIN 3.6V TO 20V VIN ON OFF C1 4.7F SHDN LT1936 COMP VC FB GND R2 20k C2 47F x2
1936 TA05a
BOOST SW
EFFICIENCY (%)
D1: DFLS140L D2: 1N4148 L1: TOKO D63CB
1.2V Step-Down Converter
D2 VIN 3.6V TO 20V VIN ON OFF C1 4.7F SHDN LT1936 COMP VC FB GND 100k C2 47F x2
1936 TA06a
BOOST SW
D1
EFFICIENCY (%)
D1: DFLS140L D2: 1N4148 L1: TOKO D63CB
U
Efficiency, 1.8V Output
90 VOUT = 1.8V TA = 25C VIN = 5V VIN = 12V 70 1.0 2.0
C3 0.22F
L1 4.7H R1 10k
D1
VOUT 1.8V 1.3A
80
1.5
POWER LOSS (W)
60 POWER LOSS 50 0 0.5 1 LOAD CURRENT (A)
0.5
0 1.5
1936 TA05b
Efficiency, 1.2V Output
80 VOUT = 1.2V TA = 25C VIN = 5V 70 65 60 0.5 55 50 0 0.5 1 LOAD CURRENT (A) POWER LOSS 0 1.5
1936 TA06b
2.0
C3 0.22F
L1 3.3H
75
VOUT 1.2V 1.3A
1.5
POWER LOSS (W)
VIN = 12V
1.0
1936f
17
LT1936
TYPICAL APPLICATIO S
2.5V Step-Down Converter
D2 VIN 3.6V TO 36V VIN ON OFF C1 4.7F SHDN LT1936 COMP VC FB GND R2 10k BOOST SW D1 R1 11k C3 1F
Efficiency, 2.5V Output
100 5.5 VOUT = 2.5V TA = 25C 5.0 VIN = 5V 80 VIN = 12V
INPUT VOLTAGE (V)
90
EFFICIENCY (%)
70
60 0 0.5 1.0 LOAD CURRENT (A) 1.5
1936 TA07b
18
U
L1 6.2H VOUT 2.5V 1.2A TA > 0C C2 47F
D1: DFLS140L D2: MBRO540 L1: TOKO D63CB
1936 TA07a
Minimum Input Voltage
VOUT = 2.5V
TO START TA = -45C
4.5 TO START TA = 25C TO RUN TA = -45C 3.5 TO RUN TA = 25C 3.0 1 100 10 LOAD CURRENT (mA) 1000
1936 TA07c
4.0
1936f
LT1936
PACKAGE DESCRIPTION
MS8E Package 8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1662)
BOTTOM VIEW OF EXPOSED PAD OPTION 1 2.06 0.102 (.081 .004) 1.83 0.102 (.072 .004)
2.794 0.102 (.110 .004)
5.23 (.206) MIN
0.42 0.038 (.0165 .0015) TYP
RECOMMENDED SOLDER PAD LAYOUT
DETAIL "A" 0 - 6 TYP
0.254 (.010)
GAUGE PLANE
0.18 (.007)
SEATING PLANE
NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
U
0.889 0.127 (.035 .005)
2.083 0.102 3.20 - 3.45 (.082 .004) (.126 - .136)
8
0.65 (.0256) BSC
3.00 0.102 (.118 .004) (NOTE 3)
8
7 65
0.52 (.0205) REF
4.90 0.152 (.193 .006)
3.00 0.102 (.118 .004) (NOTE 4)
1 0.53 0.152 (.021 .006)
DETAIL "A"
23
4 0.86 (.034) REF
1.10 (.043) MAX
0.22 - 0.38 (.009 - .015) TYP
0.65 (.0256) BSC
0.127 0.076 (.005 .003)
MSOP (MS8E) 0603
1936f
19
LT1936
TYPICAL APPLICATIO
D2 VIN 3.6V TO 20V VIN ON OFF C1 4.7F SHDN LT1936 COMP VC FB GND BOOST SW
2.5V Step-Down Converter
5.5 C3 0.22F L1 8.2H R1 11k
INPUT VOLTAGE (V)
D1: DFLS140L D2: 1N4148 L1: TOKO D63CB
RELATED PARTS
PART NUMBER LT1676 LT1765 LT1766 LT1767 LT1776 LT1933 LT1940 LT1956 LT1976 LT3010 LTC(R)3407 LTC3412 LTC3414 LT3430/LT3431 DESCRIPTION 60V, 440mA (IOUT), 100kHz, High Efficiency Step-Down DC/DC Converter 25V, 2.75A (IOUT), 1.25MHz, High Efficiency Step-Down DC/DC Converter 60V, 1.2A (IOUT), 200kHz, High Efficiency Step-Down DC/DC Converter 25V, 1.2A (IOUT), 1.25MHz, High Efficiency Step-Down DC/DC Converter 40V, 550mA (IOUT), 200kHz, High Efficiency Step-Down DC/DC Converter 600mA, 500kHz, Step-Down Switching Regulator in SOT-23 25V, Dual 1.4A (IOUT), 1.1MHz, High Efficiency Step-Down DC/DC Converter 60V, 1.2A (IOUT), 500kHz, High Efficiency Step-Down DC/DC Converter 60V, 1.2A (IOUT), 200kHz, High Efficiency Step-Down DC/DC Converter with Burst Mode(R) Operation 80V, 50mA, Low Noise Linear Regulator Dual 600mA (IOUT), 1.5MHz, Synchronous Step-Down DC/DC Converter 2.5A (IOUT), 4MHz, Synchronous Step-Down DC/DC Converter 4A (IOUT), 4MHz, Synchronous Step-Down DC/DC Converter 60V, 2.75A (IOUT), 200kHz/500kHz, High Efficiency Step-Down DC/DC Converters COMMENTS VIN: 7.4V to 60V, VOUT(MIN) = 1.24V, IQ = 3.2mA, ISD = 2.5A, SO-8 Package VIN: 3V to 25V, VOUT(MIN) = 1.20V, IQ = 1mA, ISD = 15A, SO-8 and 16-Lead TSSOPE Packages VIN: 5.5V to 60V, VOUT(MIN) = 1.20V, IQ = 2.5mA, ISD = 25A, 16-Lead TSSOP/TSSOPE Packages VIN: 3V to 25V, VOUT(MIN) = 1.20V, IQ = 1mA, ISD = 6A, MS8/MS8E Packages VIN: 7.4V to 40V, VOUT(MIN) = 1.24V, IQ = 3.2mA, ISD = 30A, N8/SO-8 Packages VIN: 3.6V to 36V, VOUT(MIN) = 1.25V, IQ = 1.6mA, ISD < 1A, ThinSOTTM Package VIN: 3V to 25V, VOUT(MIN) = 1.2V, IQ = 3.8mA, ISD < 1A, 16-Lead TSSOPE Package VIN: 5.5V to 60V, VOUT(MIN) = 1.20V, IQ = 2.5mA, ISD = 25A, 16-Lead TSSOP/TSSOPE Packages VIN: 3.3V to 60V, VOUT(MIN) = 1.20V, IQ = 100A, ISD < 1A, 16-Lead TSSOPE Package VIN: 1.5V to 80V, VOUT(MIN) = 1.28V, IQ = 30A, ISD < 1A, MS8E Package VIN: 2.5V to 5.5V, VOUT(MIN) = 0.6V, IQ = 40A, ISD < 1A, 10-Lead MSE Package VIN: 2.5V to 5.5V, VOUT(MIN) = 0.8V, IQ = 60A, ISD < 1A, 16-Lead TSSOPE Package VIN: 2.3V to 5.5V, VOUT(MIN) = 0.8V, IQ = 64A, ISD < 1A, 20-Lead TSSOPE Package VIN: 5.5V to 60V, VOUT(MIN) = 1.20V, IQ = 2.5mA, ISD = 30A, 16-Lead TSSOPE Package
1936f
Burst Mode is a registered trademark of Linear Technology Corporation. ThinSOT is a trademark of Linear Technology Corporation.
20
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 FAX: (408) 434-0507
U
Minimum Input Voltage
VOUT = 2.5V CONNECTING THE BOOST CIRCUIT TO THE INPUT LOWERS THE MINIMUM INPUT VOLTAGE TO RUN AND TO START TO LESS THAN 3.7V AT ALL LOADS 5.0 VOUT 2.5V 1.3A D1 4.5 4.0 R2 10k C2 47F 3.5
1936 TA08a
3.0
1
100 10 LOAD CURRENT (mA)
1000
1936 TA08b
LT/TP 0305 500 * PRINTED IN USA
www.linear.com
(c) LINEAR TECHNOLOGY CORPORATION 2005

▲Up To Search▲

Price & Availability of LT1936

	To Download LT1936 Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .